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    • 专利摘要:
    SWITCHING POWER SUPPLY CIRCUIT. Reactor characteristics are correctly adjusted in an interleaved power factor correction circuit in which reinforcement switches are adopted, in order to improve the exchange between the improvement in efficiency and the prevention of audible sound. A reactor (L1), a diode (D1), and a switching element (S1) connected to a path (LH1) constitute a reinforcement circuit (B1), and a reactor (L2), a diode (D2), and a switching element (S2) connected to a path (LH2) constitutes a reinforcement circuit (B2). The reinforcement circuits (B1, B2) also function as a power factor correction circuit to correct a power factor on the input side. Rotating bottlenecks are adopted as the reactors (L1, L2).
    公开号:BR112012024353B1
    申请号:R112012024353-5
    申请日:2011-02-22
    公开日:2021-02-09
    发明作者:Norio Sakae；Toshio Yabuki；Kazuhiro Ohshita
    申请人:Daikin Industries, Ltd.；
    IPC主号:
    专利说明:

    Technical Field
    [0001] The present invention relates to a switching power supply circuit, and more particularly, a power factor correction circuit. Background of the Technique
    [0002] Patent Document 1 describes a DC-DC current resonant type converter, and also describes a converter provided with a rotary choke type rotary choke coil (hereinafter, "rotary choke") and a resonance choke coil connected in parallel with it.
    [0003] Non-Patent Document 1 describes a pair of power factor correction circuits operating in a critical current mode and in an interleaved manner (hereinafter, merely referred to as an "interleaved power factor correction circuit" "). In the interleaved power factor correction circuit, a pair of reinforcement switch circuits are connected in parallel, and reactors, diodes and switching elements are provided. For example, a MOS field effect transistor is adopted as a switching element.
    [0004] Non-Patent Document 2 describes a direct current mode, a critical current mode and a non-direct current mode with respect to the current flowing through a reactor, and also describes a rotating choke. Prior Art Documents Patent Document
    [0005] Patent Document 1: Japanese Patent Application Published No9-224369 (1997) Non-Patent Documents
    [0006] Non-Patent Document 1: Mamoru Kitamura, ‘Critical Mode to Create Power Supplement against 1.5 kW Low / Interleaved Noise PFC IC R2A20112’, Transistor Gijutsu, May 2008, CQ Publishing Co., Ltd., pp. 176-184.
    [0007] Non-Patent Document 2: Morio Satoh, 'LC element power supply circuit' [online] Available at: <http://www.tdk.co.jp/tjbcd01/bcd23_26.pdf> retrieved at 5 March 2010, pp. 12-13 (THE HOTLINE vol. 25, pp. 39 and 40). Summary of the invention Problems to be solved by the invention
    [0008] The operation of a power factor correction circuit in a direct current mode results in the switching being performed when a current is flowing through a diode, which is not desired in terms of an increase in electrical noise . Therefore, it is desirable to use the power factor correction circuit in an alternating current mode or a critical current mode. For example, in an interleaved power factor correction circuit, the critical current mode is normally adopted for current to flow through a reactor.
    [0009] A large inductance to the reactor in the power factor correction circuit tends to result in direct current mode when a large current flows through the power factor correction circuit. Alternatively, even if the power factor correction circuit can be operated in critical current mode, not in direct current mode, the switching frequency decreases to cause a large current to flow through it when the inductance is large. This is not desirable in that the frequency of mechanical vibration has a tendency to introduce an audible range to cause audible noise.
    [00010] Therefore, in the case of adopting a power factor correction circuit, particularly, an interleaved power factor correction circuit, in which a critical current mode is adopted is used for large power, it is desired to decrease the reactor inductance.
    [00011] However, if the reactor's inductance is decreased in critical current mode, the switching frequency becomes high in a situation where a load is small. This incurs problems such as an increase in noise that occurs with switching and a decrease in efficiency due to an increase in switching loss of a switching element in a power factor correction circuit.
    [00012] When a power factor correction circuit is operated in an alternating current mode, it is possible to prevent the switching frequency from increasing in a situation where a reactor's inductance is small and a load is small as well. However, without an increase in the switching frequency, the current flowing through the switching element increases, and not only does a loss of switching increase, but also a loss of conduction of the switching loss increases, leading to a reduction in efficiency.
    [00013] Therefore, an objective of the present invention is to provide a switching power supply circuit to optimize the trade-off between preventing efficiency reduction and preventing audible sound by correctly adjusting characteristics of a reactor in a correction circuit. of the power factor in which a boost switch is adopted. Troubleshooting Devices
    [00014] A first aspect of the present invention relates to a switching power supply circuit (4) supplying a DC current to an inverter (5) that drives a refrigerant compressor (7) supplied in a refrigerant cycle (900) and operating in a critical current mode or in an alternating current mode. Included are: a first and a second entry end (P1, P2); a first and a second outlet ends (P3, P4); a first path (LH1) connecting the first inlet end and the first outlet end; a first reactor (L1) provided on the first leg; a first diode (D1) connected in series with the first reactor on the side of the first outlet end on the first path and having an anode directed next to the first reactor; a second path (LL) connecting the second inlet end and the second outlet end; and a first switching element (S1) provided between a point located between the first reactor and the first diode and the second path.
    [00015] An inductance of the first reactor takes a first value (L11) at a maximum value of a current flowing through the first reactor when the refrigerant cycle operates at intermediate operating capacity or capacity less than the intermediate operating capacity, and the inductance of the first reactor obtains the second value (L12) less than the first value in a maximum value of a current flowing through the first reactor when the refrigerant cycle transiently operates at capacity exceeding the capacity of full load operation and when the refrigerant cycle operates at full load operating capacity.
    [00016] According to a second aspect of the present invention, in the switching power supply circuit of the first aspect, the inductance of the first reactor takes the first value at a maximum value of a current flowing through the first reactor when the refrigerant cycle operates at a nominal capacity.
    [00017] According to a third aspect of the present invention, in the switching power supply circuit of the first or second aspect, the inductance of the first reactor takes on a value to make a switching frequency of the first switching element equal to or greater than than an audible frequency.
    [00018] According to a fourth aspect of the present invention, the switching power supply circuit of any of the first, second or third aspects further includes: a third path (LH2) connecting to the first inlet end and the first end departure and differing from the first route; a second reactor (L2) provided on the third leg; a second diode (D2) connected in series with the second reactor on the side of the first outlet end on the third path and having an anode directed to the side of the second reactor; and a second switching element (S2) provided between a point located between the second reactor and the second diode and the second path (LL) and being made conductive exclusively by the first switching element.
    [00019] According to a fifth aspect of the present invention, in the switching power supply circuit of any of the first, second, third and fourth aspects, the first switching element and the first reactor are mounted on the same circuit board printed.
    [00020] The refrigerating cycle is, for example, an air conditioner. Effects of the Invention
    [00021] The operating capacity of the refrigerant cycle varies over a wide range from the lower capacity than the intermediate operating capacity to the full load operating capacity, and the inverter load varies greatly as well. According to the first aspect of the power factor correction circuit of the present invention, the noise generated by the switching power supply circuit does not readily reach the audible sound range even if the inverter load is large, so that a loss caused in a case of the small load is lessened.
    [00022] According to the second aspect of the power factor correction circuit of the present invention, a loss is also reduced in the nominal capacity.
    [00023] According to the third aspect of the power factor correction circuit of the present invention, the noise generated by the switching power supply circuit does not reach the audible sound range, so that the generation of noise is prevented.
    [00024] According to the fourth aspect of the power factor correction circuit of the present invention, a so-called interleaving operation is achieved, whereby waves from the current input to the power factor correction circuit are reduced .
    [00025] According to the first to fourth aspects of the power factor correction circuit of the present invention, the first reactor generates a small amount of heat. In this way, if the first reactor is mounted on the printed circuit board on which the first switching element is mounted, the first switching element is not much affected by the generation of heat, which is particularly preferred in a case where a semiconductor element is adopted as the first switching element. Therefore, according to the fifth aspect of the power factor correction circuit of the present invention, the connection line for connecting the substrate on which the first switching element is mounted and the first reactor is not required, which is not only reduces the number of parts, but also prevents noise resulting from the connecting line.
    [00026] These and other objectives, characteristics, aspects and advantages of the present invention will become more apparent from the following detailed description of the present invention when obtained in conjunction with the attached drawings. BRIEF DESCRIPTION OF THE DRAWINGS
    [00027] FIG. 1 is a circuit diagram showing a configuration of a power factor correction circuit according to an embodiment of the present invention; FIG. 2 is a graph showing an operation in a direct current mode; FIG. 3 is a graph showing an operation in an alternating current mode; FIG. 4 is a block diagram illustrating a configuration of an air conditioner 900; FIG. 5 is a graph showing a reactor inductance adopted in the power factor correction circuit; FIG. 6 is a graph showing a current flowing through a reactor; FIG. 7 is another graph showing a current flowing through the reactor; FIG. 8 is yet another graph showing a current flowing through the reactor; FIG. 9 is a graph showing a reactor inductance adopted in the power factor correction circuit; FIG. 10 is a diagram showing the appearance of a power factor 4 correction circuit; FIG. 11 is a circuit diagram showing an interleaved power factor correction circuit configuration according to the embodiment of the present invention; and FIG. 12 is a graph showing an operation of the interleaved power factor correction circuit. Modality for Carrying Out the Invention
    [00028] As illustrated in FIG. 1, a switching power supply circuit according to the present embodiment includes input ends P1 and P2, output ends P3 and P4, a reactor L1, a diode D1, a switching element S1, and a filtration capacitor final C.
    [00029] A DC voltage is applied between the input ends P1 and P2. For example, a diode rectifier circuit (not shown) is connected to input ends P1 and P2. The diode rectifier circuit rectifies an AC voltage from an AC power supply, and applies a DC voltage after rectification between the input ends P1 and P2. Here, a potential applied to the input end P2 is less than a potential applied to the input end P1. It is not necessarily required that the diode rectifier circuit be connected to the input ends P1 and P2. It is enough that any configuration to apply a DC voltage between the input ends P1 and P2 is connected to the input ends P1 and P2.
    [00030] The L1 reactor is supplied in an LH1 path connecting the input end P1 and the output end P3.
    [00031] Diode D1 is connected in series with reactor L1 on the side of the first output end P3 on the path LH1. The D1 diode has an anode directed to the L1 reactor.
    [00032] The switching element S1 is provided between a point located between the reactor L1 and diode D1 and a path LL connecting the input end P2 and the output end P4. Note that FIG. 1 illustrates the switching element S1 as a MOS field effect transistor, which is not limited to this. The switching element S1 can be, for example, a bipolar transistor with isolated port or a bipolar transistor.
    [00033] The term "MOS" was used for the laminated metal / oxide / semiconductor structure, which was named after the initial letters of Metal-Oxide-Semiconductor. Particularly, in a field effect transistor having a MOS structure ("MOS field effect transistor"), however, improvements have been made to materials from a door insulation film and a door electrode from the point of view of , for example, recent improvements in the integration and manufacturing process.
    [00034] For example, polycrystalline silicone has now been adopted as the door electrode material in place of metal primarily from the point of view of forming a source and a drain in a self-aligning manner. Although a material having a high dielectric constant is adopted as the material of the door insulation film from the point of view of improving electrical characteristics, the material is not necessarily limited to oxides.
    [00035] Therefore, the adoption of the term "MOS" is not necessarily limited to the laminated metal / oxide / semiconductor structure, and the present specification is not based on such a limitation. That is, in view of common technical knowledge, "MOS" here is not only used as an abbreviation derived from its origin of the word, but it also has a broad meaning including a laminated conductor / insulator / semiconductor structure.
    [00036] The final filtration capacitor C is provided between the output ends P3 and P4. The final filtration capacitor C filters the applied DC voltage from the input ends P1 and P2 through the reactor L1, the diode D1, and the switching element S1.
    [00037] The reactor L1, diode D1, and the switching element S1 that are connected to the path LH1 constitute a reinforcement circuit B1, reinforcement circuit B1 constitutes a circuit of supply of switching energy together with the final filtration capacitor C. Booster circuit B1 also functions as a power factor correction circuit to correct the PF on the input side.
    [00038] Based on an IL1 current flowing through the L1 reactor, controller 6 controls conduction / non-conduction of switching element S1 in critical current mode, as shown in, for example, FIG. 2 or in an alternating current mode as shown in, for example, FIG. 3.
    [00039] In the present modality, an L1s reactor is provided to detect the IL1 current. The L1s reactor constitutes a transformer together with the L1 reactor. Controller 6 detects a current flowing through the L1s reactor and estimates the current IL1.
    [00040] FIG. 4 is a block diagram illustrating the configuration of an air conditioner 900 which is a refrigerating cycle in which a power factor 4 correction circuit according to the present modality is adopted. Air conditioner 900 includes an indoor unit 901 and an outdoor unit 902. The indoor unit 901 and the outdoor unit 902 are both supplied with the AC power from a commercial power supply 1, and a total amount of the AC power is indicated as a W power. The aforementioned booster circuit B1 can be adopted as the power factor 4 correction circuit. In place of the air conditioner 900, a refrigerant cycle of the well-known heat pump type, for example , a water heater can be adopted.
    [00041] The air conditioner 900 is supplied with a refrigerating compressor 7 and an inverter 5 activating this in the external unit 902. The power factor correction circuit 4 operates in a critical current mode or an alternating current mode and supplies a DC direct current to the inverter 5.
    [00042] A diode rectifier circuit 3 is also provided on external unit 902, which rectifies an AC voltage from the commercial power supply 1 and supplies a DC voltage after rectification for the power factor correction circuit 4.
    [00043] Controller 6 controls not only the operation of the power factor correction circuit 4, but also that of the inverter 5.
    [00044] The driving / non-driving control technique of switching element S1 and inverter 5 is well known, which is not further described here.
    [00045] Here, controller 6 includes a microcomputer and a storage device. The microcomputer performs process steps (in other words, procedures) described in a program. The storage device can be configured with, for example, one or a plurality of several storage devices such as a read-only memory (ROM), a random access memory (RAM), a rewritable non-volatile memory (for example, a rewritable memory). programmable erasable for ROM (EPROM)), and a hard disk device. The storage device stores various types of information, data, and the like, and also provides a work area to run the program. The microcomputer can be understood for the function as several devices corresponding to the process steps described in the program or it can be understood to implement several functions corresponding to the process steps. Controller 6 is not limited to the above, and various procedures performed by controller 6, or various devices or functions implemented in this way, can be partially or fully implemented as hardware.
    [00046] In the present modality, a rotary choke is adopted as an L1 reactor.
    [00047] In FIG. 5, a normal reactor inductance and a rotating choke inductance are indicated by a curve 101 and a curve 102, respectively. The case is illustrated here where the inductances of those are equal to each other in an area of a small current.
    [00048] The switching power supply circuit according to the present mode is triggered causing a current to flow through the L1 reactor in an alternating current mode or a critical current mode. Normally, the current input to the input ends P1 and P2 is the DC rectified by the diode rectifier circuit 3 and, for example, how a sine wave is introduced into the diode rectifier circuit 3.
    [00049] The description of the IL1 current flowing through the L1 reactor is given below in a case where a rotary choke is adopted as the L1 reactor.
    [00050] As indicated by curve 102 in FIG. 5, the rotating choke inductance shows almost flat characteristics in a large current area, and the inductance in the area of a small current flowing through the rotating choke is greater than the inductance in the area of a large current. In other words, curve 102 has at least two inflection points.
    [00051] The L1, L2 and L3 values of the IL1 current correspond to the maximum currents when the power W supplied to the external unit 902 takes the immediate operating power consumption, the nominal operating power consumption, and the operating power consumption. full load (see JIS C9612), respectively. That is, the maximum value of the current IL1 takes the value I1 when the air conditioner 900 operates at the intermediate operating capacity, the maximum value of the current IL1 takes the value 12 when the air conditioner 900 performs a nominal operation, and the value maximum current IL1 is set to 13 when the air conditioner 900 operates at full load (I3> I2> I1). Alternatively, the rated operating power consumption can be conformed to the ISO 5151-commercial power supply 1, in this case, the immediate power consumption is understood as one half of the rated operating power consumption. Full load operation capacity is the capacity in which an air conditioner is capable of continuous production, which is specified by a producer of the air conditioner, in a cooling operation, and is 1.38 times the power consumption of full load operation by heating at a low temperature defined in the above pattern in a heating operation.
    [00052] The inductance of the L1 reactor takes the value L11 in a case where the current IL1 when the air conditioner 900 operates at the intermediate operating capacity or at the capacity lower than the intermediate operating capacity takes the maximum value I1, and takes a second value L12 (<L11) in a case where the current IL1 when the air conditioner 900 operates at full load operating capacity or transiently operates at capacity exceeding the full load operating capacity takes the maximum value I1.
    [00053] FIG. 6 is a graph showing the case where the current IL1 takes a value less than the value I1. A dashed line added to the IL1 chain shows an outline of an IL1 chain housing. The enclosure is controlled to have a sine wave conformation (for example, see FIG. 14 and the similar to Non-Patent Document commercial power supply 1), and therefore, if the IL1 current is small, the frequency for conduction / non-conduction of the switching element S1 (ie the switching frequency) becomes high in the critical current mode, which tends to result in a large switching loss. If the current IL1 is small, the current caused to flow when switching element S1 is in condition increases in alternating current mode unless the switching frequency is increased. This incurs increases in switching loss as well as loss of conduction, leading to a decrease in efficiency. For this reason, it is desired that the L11 value of the L1 reactor inductance is set high so that the current IL1 does not rise readily if the switching element S1 is the final filtering capacitor C.
    [00054] In this way, in a case where the air conditioner 900 is operated at the capacity of intermediate operation or less, those losses can be reduced which allows an efficient operation. Generally, the times when the outdoor temperature reaches a temperature at which an air condition is required (for example, see Table 3 and Table 6 in Appendix 3 to JIS C9612) are centered on the temperature at which an air conditioner is required to operate intermediate capacity or less. For this reason, the annual performance factor (APF; see Appendix 3 of JIS C9612) is improved to increase efficiency in a case of intermediate or lower operating capacity.
    [00055] In order to further improve the annual performance factor, the rotary choke inductance adopted as the L1 reactor can take the value (L11) until the IL1 current reaches the I2 value corresponding to the nominal operation, as indicated by curve 102 in the FIG. 5.
    [00056] Generally, the loss of conduction of a bipolar isolated transistor is expressed by the product of the current flowing through the bipolar isolated transistor and the voltage between its emitter and collector. In the meantime, the conduction loss of a MOS field effect transistor is expressed by the product of a square of the current flowing through the MOS field effect transistor and its resistance. Typically, the voltage between the emitter and the collector of the bipolar isolated-door transistor is approximately 1.5 V, and the resistance of the MOS field effect transistor is approximately 0.2 Q. Therefore, a field effect transistor MOS has a lower conduction loss than an isolated gate bipolar transistor when the flowing current is 7.5 A or less.
    [00057] In view of the comparison of conduction losses, it is desired to adopt a MOS field effect transistor as the switching element S1 to reduce a loss when the air conditioner 900 is operated at the intermediate operating capacity or less and, therefore, way, intensifying the annual performance factor.
    [00058] FIG. 6 applies the current flowing through a normal reactor corresponding to the inductance of curve 101 as well as the current flowing through a rotating choke corresponding to the inductance of curve 102. This is because both inductances coincide with each other in the area where the current IL1 is less than the I1 value.
    [00059] Considered here is the case where it is required to increase the operating capacity to make the IL1 current large. FIG. 7 is a graph in a case where the operating capacity is high and the flowing current IL1 exceeds the value I2 (> I1) when a normal reactor whose inductance is indicated by curve 101 is used. As shown in FIG. 5, curve 101 shows a sharp decrease approximately after the IL1 exceeds the I2 value, and a slope of the decrease becomes more abrupt at the I3 value (> I2).
    [00060] Even if the current IL1 exceeds the value I2, the slope of the waveform of the current IL1 is assumed to be the same (see a dashed line of a triangle wave in FIG. 7) as shown in the graph shown in FIG. 6 except that the L1 reactor inductance decreases. However, the inductance of the L1 reactor decreases, and in this way, the slope of the current IL1 becomes inclined when exceeding the value I2, which causes a large current to flow (see a solid line of a graph in FIG. 7 ). As a result, a portion even though exceeding the I3 value is generated in the IL1 current, and its slope becomes more steep. In this way, the IL1 current housing is widely distorted, which is not desirable from the point of view of harmonic prevention. Furthermore, it is worrying that the switching frequency may decrease and introduce an audible frequency range if the critical current mode is adopted, and, moreover, it is worrying that a deviation to the direct current mode may tend to occur and an electrical noise may increase if alternating current mode is adopted.
    [00061] However, FIG. 8 is a graph in a case where the operating capacity is high and the flowing current IL1 exceeds the value 12 when a rotating choke whose inductance is indicated by curve 102 is used as the L1 reactor. As indicated by curve 102, the inductance decreases temporarily as the IL1 current becomes greater, but the inductance does not decrease much even if the IL1 current becomes much greater. Therefore, if the current IL1 exceeds the value 12, the slope of the current IL1 does not become too steep even when exceeding the value 12 and does not exceed the value 13. In this way, the waveform of the IL1 current housing is not very distorted, and an average value of the enclosure (see a line like current in FIG. 8) becomes close to a sine wave.
    [00062] The air conditioner 900 is generally operated in order to perform a maximum or less operation, but in some cases, it is transiently operated exceeding the maximum operation. If it is desired that the L1 reactor inductance should not decrease to maintain efficiency even in those cases. When the current IL1 is large, the loss of conduction of the switching element S1 becomes dominant as a loss of the reinforcement circuit B1, and the loss due to a loss of copper from the L1 reactor increases in proportion to a square of the current IL1. Therefore, it is desired to prevent the inductance from becoming small and a peak value of the IL1 current from becoming large (similar to the waveform shown in FIG. 7).
    [00063] However, it is not desired to increase the inductance to prevent operation in a direct current mode or to prevent the switching frequency from becoming small in a critical current mode. In this way, the inductance is desired to take the constant value L12 when the current IL1 takes the value 13 or greater.
    [00064] A description is given of the fact that the inductance of the L1 reactor in which a rotary choke is adopted is constant at the value L12 in the area where the current IL1 is the value 13 or greater. As in FIG. inverter 5, the inductance is indicated by curve 102. Note that FIG. 9 shows the area close to the value 13 taken by the IL1 current, which is wider compared to FIG. 5.
    [00065] Each of the curves J1 and J2 indicates a value of the L1 reactor inductance in a case where the frequency of mechanical vibration becomes constant.
    [00066] According to Non-Patent Document 1, if a minimum AC voltage input (effective value) to diode rectifier circuit 3, the output voltage of the reinforcement circuit B1, the power factor, and efficiency are constant , the inductance of reactor L1 is inversely proportional to the product of a maximum value of the output power of the reinforcement circuit B1 and a minimum value of PWM frequency. The maximum value of the output power can be considered to be proportional to the product of the output voltage and the output current, and the minimum value of the PWM frequency can be considered to be a minimum value of the switching frequency. Therefore, the inductance of the L1 reactor is inversely proportional to the current IL1 if the switching frequency is fixed and becomes smaller as the switching frequency becomes higher.
    [00067] The description above reveals that the inductance values indicated by curves J1 and J2 become smaller as the current IL increases. The value of the frequency corresponding to the inductance indicated by curve J1 is greater than the value of the frequency corresponding to the inductance indicated by curve J2, which are, for example, 20 kHz and 10 kHz, respectively.
    [00068] Each of the K1 and K2 curves indicates the inductance value of the L1 reactor in a case where the efficiency of the reinforcement circuit B1 is constant. However, depending on the efficiency, a loss of copper from the L1 reactor is not taken into account. In this way, efficiency becomes lower as the switching loss becomes greater and the switching loss becomes greater as the switching frequency becomes greater. Also taking into account that the reinforcement circuit B1 operates not only in an alternating current mode, but also in a critical current mode to increase the current IL1 while decreasing the switching frequency, a peak of the current output of the reinforcement circuit. B1 during a period in which the switching is not done, it is caused to be increased by reducing an inductance value. For this reason, in order to make the current IL1 large in equal efficiency, the inductance is made smaller as the current IL1 is greater.
    [00069] The above description reveals that the efficiency values indicated by curves K1 and K2 become smaller as the current IL1 increases. The efficiency value corresponding to the inductance indicated by the K1 curve is greater than the efficiency value corresponding to the inductance indicated by the K2 curve, which are, for example, 95% and 97%, respectively.
    [00070] However, the efficiency of the reinforcement circuit B1 is hindered by a loss of copper from the L1 reactor in addition to the switching loss described above. The copper loss of the L1 reactor is proportional to a square of the IL1 current. An R1 curve indicates the loss of copper, and its rate of increase becomes greater as the current IL1 increases.
    [00071] From the above, it is desired that the L1 reactor inductance is less than the value indicated by the J1 curve from the point of view that the frequency of mechanical vibrations does not readily introduce an audible range and is greater than the values indicated curves K1 and R1 from the point of view of intensifying efficiency. In particular, from the point of view that the power is supplied for an air conditioner required to have an operating capacity equal to or more than the maximum capacity operation even in a transient manner, the inductance is desired to be greater than the indicated value curve R1 in the area where the current IL1 is approximately I3 or more.
    [00072] If the inductance is greater than the value indicated by the JI curve, and, for example, the switching frequency becomes less than 20 kHz, that itself does not mean that the modality cannot be performed. If the inductance is less than the value indicated by curve J2 even if it is greater than the value indicated by curve J1, and, for example, if the switching frequency is greater than 15 kHz, in some cases, a operation of the refrigerant compressor 7, the wind noise of a fan (not shown) normally adopted in the external unit 902, or the noise resulting from the frequency of the inverter conveyor 5 is greater than the noise resulting from the switching frequency of the correction circuit of the power factor 4. In such cases, it is not required to take a specific measure against the noise generated from the power factor 4 correction circuit. That is, if the switching frequency does not decrease to fall below approximately a high frequency limit of an audible range, it can be recognized that the effects of the present modality are achieved.
    [00073] As described above, in the rotating choke, the inductance shows almost flat characteristics in the area of a large current, and thus it is possible to maintain the large inductance also in a case where the IL1 current flowing through the L1 reactor adopting this it's big. This prevents a decrease in efficiency while preventing the switching frequency from reaching the audible frequency range and preventing noise.
    [00074] It is possible to prevent the waveform of an output current from becoming slanted. That is, an effect in which harmonics of the output current can be prevented is realized. In addition, another effect is achieved than a small current element, for example, a field effect transistor can be adopted as the switching element S1. In addition, yet another effect is achieved that a decrease in switching frequency is prevented.
    [00075] The inductance in the area where the IL1 flowing through the L1 reactor is small is greater than the inductance in the area where the IL1 current is large, which makes it possible to intensify efficiency in the area where the IL1 current is small.
    [00076] Typically, the operating capacity of an air conditioner varies in a wide range from the lower capacity than the intermediate operating capacity to the full load operating capacity, and the inverter load 5 (for example, compressor 7 ) also varies widely. Therefore, the following effect is achieved by the L1 reactor inductance taking the value L11 when the air conditioner 900 operates at the intermediate operating capacity and at the lower capacity than the intermediate operating capacity and taking the value L12 (<L11) when the air conditioner 900 transiently operates at capacity exceeding the full load operating capacity and when the air conditioner 900 operates at full load operating capacity as described above. That is, even if the load of the inverter 5 is large, the noise of the switching power supply circuit, among others, the power factor correction circuit 4, does not readily reach the audible sound range, and a loss it is caused in the event that a small load is reduced.
    [00077] The inductance of the L1 reactor takes the value L11 even when the air conditioner 900 operates at the nominal capacity, so that a loss is also reduced at the nominal capacity.
    [00078] The L1 reactor inductance takes a value to make the switching frequency equal to or greater than the audible frequency, so that the noise generated by the switching power supply circuit, among others, the factor correction circuit power 4, does not reach the audible sound range, and noise generation is avoided.
    [00079] FIG. 10 is a diagram showing the appearance of the power factor correction circuit 4. In the power factor correction circuit 4, the paths LL and LH1, the input ends P1 and P2, and the output ends P3 and P4 are implemented on a printed circuit board 40. Additionally, reactors L1 and L1s, diode D1, and switching element S1 are mounted on printed circuit board 40.
    [00080] As described above, the heat generation of the L1 reactor is reduced by increasing the inductance of the L1 reactor particularly in the area where the IL1 current is large. Therefore, it is not required to separate and thermally isolate the reactor L1 from the printed circuit board 40 on which the switching element S1 is mounted. In other words, even if the reactor L1 is mounted on the printed circuit board 40 on which the switching element S1 is mounted, the first switching element S1 is not affected much by the generation of heat. This is particularly preferable in the case where a semiconductor element is adopted as the switching element S1. The reactor L1 is mounted on the printed circuit board 40 on which the switching element S1 is mounted, whereby the connection line for connecting the reactor L1 and the printed circuit board 40, becomes unnecessary. As a result of omitting the aforementioned connecting line, the number of parts can be reduced, and in addition, the noise resulting from the connecting line can be avoided.
    [00081] An interleaved power factor correction circuit can be adopted as the power factor correction circuit 4. FIG. 11 is a circuit diagram showing the interleaved power factor correction circuit configuration. The configuration shown in FIG. 11 is obtained by providing a switching element S2, reactors L2 and Ls2, a diode D2, and a path LH2 for the configuration shown in FIG. 1.
    [00082] The L2 reactor is supplied in an LH2 path connecting the input end P1 and the output end P3. The diode D2 is connected in series with the reactor L2 on the side of the output end P3 in the path LH2. The D2 diode has an anode directed to the L2 reactor. The switching element S2 is provided between a point located between the reactor L2 and diode D2 and the path LL. Similar to switching element S1, switching element S2 is not limited to a MOS field effect transistor and can be an isolated gate bipolar transistor, a bipolar transistor, or the like.
    [00083] The reactor L2, diode D2 and switching element S2 connected to the path LH2 constitute a reinforcement circuit B2. The reinforcement circuits B1 and B2 function as the power factor correction circuit 4 to correct the input side power factor. The power factor correction circuit 4 constitutes a switching power supply circuit together with the final filtering capacitor C. Controller 6 controls the conduction / non-conduction of the switching elements S1 and S2 not only based on the current IL1 , but also based on the IL2 current flowing through the L2 reactor, as shown in, for example, FIG. 12. The current IL flowing between the input ends P1 and P2 is a sum of the currents IL1 and IL2.
    [00084] An L2s reactor is provided to detect the IL2 current, similarly to the L1s reactor. The L2s reactor constitutes a transformer together with the L2 reactor. Controller 6 detects the current flowing through the L2s reactor and estimates the IL2 current.
    [00085] The switching elements S1 and S2 are made conductive in an exclusive way, and the power factor correction circuit 4 operates in a critical current mode or an alternating current mode. The technique of controlling conduction / non-conduction of the switching elements S1 and S2 is well known as an interleaved operation, and therefore its description is not additionally given.
    [00086] In the power factor 4 correction circuit mentioned above, a rotary choke having the aforementioned characteristics is adopted at least as the L1 reactor, whereby the switch between efficiency enhancement (or even harmonic prevention) and audible sound prevention is improved.
    [00087] In the example mentioned above, the description was given of a difference between the inductance of the L1 reactor at the maximum value of the current IL1 when an air conditioner is operated at the intermediate operating capacity or less or the nominal operating capacity and inductance of the L1 reactor at the maximum value of the current IL1 when an air conditioner is operated different from the intermediate operating capacity or less or in the nominal operating capacity. However, it is apparent that the effects mentioned above can be achieved if the inductance has a large flat area in the case of the small current IL1 and has a small flat area in the case of the large current IL1.
    [00088] Similarly if a rotary choke is used as the L2 reactor, effects can be achieved that the harmonics of an output current are prevented, a small current element is adopted as the switching element S2, and the efficiency is enhanced in an area where a current is small.
    [00089] It is desired to use rotating chokes for both L1 and L2 reactors. However, it is apparent that even if a rotary choke is used for any of the L1 and L2 reactors, the effects mentioned above can be achieved, contrary to the case where normal reactors are used for both L1 and L2 reactors.
    [00090] Although the invention has been shown and described in detail, the foregoing description is, in all respects, illustrative and restrictive. It is, therefore, understood that numerous modifications and variations can be designed without departing from the scope of the invention.
    权利要求:
    Claims (10)
    [0001]
    1. Power factor correction circuit (4) supplying a DC direct current to an inverter (5) that drives a refrigerant compressor (7) supplied in a refrigerant cycle (900) and operating in a critical current mode or a alternating current, the circuit comprising: first and second ends (P1, P2); first and second outlet ends (P3, P4); a first path (LH1) connecting said first entry end and said first exit end; a first reactor (L1) provided on said first path (LH1); a first diode (D1) connected in series with said first reactor (L1) on said side of the first outlet end on said first path (LH1) and having an anode directed to said side of the first reactor; a second path (LL) connecting said second inlet end (P2) and said second outlet end (P4); and a first switching element (S1) provided between a point located between said first reactor (L1) and said first diode (D1) and said second path (LL), characterized by the fact that an inductance of said first reactor (L1) takes a first value (L11) in a maximum value of a current flowing through the first reactor (L1) when said refrigerant cycle (900) operates with intermediate operation capacity or less capacity than said intermediate operation capacity , and the inductance of said first reactor (L1) takes a second value (L12) less than said first value (L11) in a maximum value of a current flowing through said first reactor (L1) when said refrigerant cycle ( 900) transiently operates at capacity exceeding the full load operation capacity and when said refrigerant cycle (900) operates at said full load operation capacity.
    [0002]
    2. Switching power supply circuit according to claim 1, characterized by the fact that the inductance of said first reactor (L1) takes said first value (L11) into a maximum value of a current flowing through said first reactor (L1) when said refrigerant cycle (900) operates at nominal capacity.
    [0003]
    3. Switching power supply circuit according to claim 1, characterized by the fact that the inductance of said first reactor (L1) takes on a value to make a switching frequency of said first switching element (S1) equal to or higher than an audible frequency.
    [0004]
    4. Switching power supply circuit according to claim 1, characterized by the fact that it comprises: a third path (LH2) connecting said first input end (P1) and said first output end (P3) and differing said first route (LH1); a second reactor (L2) provided on said third path (LH2); a second diode (D2) connected in series with said second reactor (L2) on said side of the first outlet end on said third path (LH2) and having an anode directed to said side of the second reactor; and a second switching element (S2) provided between a point located between said second reactor (L2) and said second diode (D2) and said second path (LL) and being made conductive exclusively of said first switching element ( S1).
    [0005]
    5. Switching power supply circuit according to claim 2, characterized by the fact that it comprises: a third path (LH2) connecting said first input end (P1) and said first output end (P3) and differing from said first route (LH1); a second reactor (L2) provided on said third path (LH2); a second diode (D2) connected in series with said second reactor (L2) on said side of the first outlet end on said third path (LH2) and having an anode directed to said side of the second reactor; and a second switching element (S2) provided between a point located between said second reactor (L2) and said second diode (D2) and said second path (LL) and being made conductive exclusively of said first switching element ( S1).
    [0006]
    6. Switching power supply circuit according to claim 1, characterized in that said first switching element (S1) and said first reactor (L1) are mounted on the same printed circuit board.
    [0007]
    7. Switching power supply circuit according to claim 2, characterized in that said first switching element (S1) and said first reactor (L1) are mounted on the same printed circuit board.
    [0008]
    Switching power supply circuit according to claim 4, characterized in that said first switching element (S1) and said first reactor (L1) are mounted on the same printed circuit board.
    [0009]
    Switching power supply circuit according to claim 5, characterized in that said first switching element (S1) and said first reactor (L1) are mounted on the same printed circuit board.
    [0010]
    10. Switching power supply circuit according to any one of claims 1 to 5, characterized by the fact that said refrigerant cycle (900) is an air conditioner.
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    法律状态:
    2020-08-25| B06F| Objections, documents and/or translations needed after an examination request according [chapter 6.6 patent gazette]|
    2020-09-15| B06U| Preliminary requirement: requests with searches performed by other patent offices: procedure suspended [chapter 6.21 patent gazette]|
    2020-12-22| B09A| Decision: intention to grant [chapter 9.1 patent gazette]|
    2021-02-09| B16A| Patent or certificate of addition of invention granted [chapter 16.1 patent gazette]|Free format text: PRAZO DE VALIDADE: 20 (VINTE) ANOS CONTADOS A PARTIR DE 22/02/2011, OBSERVADAS AS CONDICOES LEGAIS. |
    优先权:
    申请号 | 申请日 | 专利标题
    JP2010-074832|2010-03-29|
    JP2010074832|2010-03-29|
    PCT/JP2011/053801|WO2011122172A1|2010-03-29|2011-02-22|Switching power source circuit|
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